Improved Beam Steering Method Using OAM Waves

1  Introduction

Modern communication and remote sensing systems require enhanced radiation features such as steerable beams for tracking, selective transmission, target recognition, and airborne and vehicle radars that scan the space with high-intensity beams [1–3]. Although beam scanning is traditionally mechanical and electrical, the two technologies are sometimes combined to permit steering in the elevation and azimuth planes. Mechanical scanning is often accomplished by designing an external system that moves the antenna along the azimuth and/or elevation planes and, despite considerable developments in the field, more conventional systems frequently include bulky devices and high maintenance costs [3]. Over the last decade, innovative solutions for electrical beam steering have been investigated to meet demands for compact and low-cost antenna designs for next-generation radar devices. Traditional techniques to provide electronic scanning mainly rely on the design of One-Dimensional (1-D) and Two-Dimensional (2-D) phased array systems whose single element must be selected and optimized based on the radiation performance and profile constraints dictated by the applications. Although 1-D and 2-D structures bring significant design complexity, they can provide steering capabilities while being fully integrated and conformable to the communication system. Recent research has concentrated on developing novel antenna designs capable of 360o azimuthal beam scanning. In [4], a horn antenna employed PIN diodes as tuning devices to dynamically change beam steering along the azimuth axis. As well in [5], a simple and compact monopole antenna with a switchable beam based on PIN diodes for millimeter-wave communication has been proposed. Another method described in [6] combined a dipole and a frequency-selective surface to enable full-range beam scanning. Also, 1-D and 2-D leaky-wave antennas are generally considered solutions for beam steering and scanning off and/or around the broadside angle [7–10]. Recently, [11–13] proposed a method for beam steering based on the Orbital Angular Momentum (OAM) features of electromagnetic waves. Various methods for generating OAM-carrying waves have been documented [14–16], and their propagation properties have been studied thus far [17]. Such waves are usually used in a variety of applications in addition to beam steering, such as cooperative OAM relaying systems [18], improving the spectrum efficiency of communications systems [19], and high-resolution imaging [20]. In [11], the authors proposed generating OAM-carrying waves by exciting a traveling wave current in two concentric, circular loops placed closely together. With appropriate selections of radii and angular locations for the excitation ports on the circular loops, a traveling wave was produced. They extended this design to generate OAM waves of multiple orders and used a superposition of these waves in beam steering. In their proposed design, two or more pairs of circular loops with different radii were concentrically placed in the same plane to produce a superimposition of multiple OAM orders easily. In [12], the authors demonstrated a lens antenna capable of a Three-Dimensional (3-D) beam steering at microwave frequencies; 360o beam steering was accomplished over the azimuth axis by utilizing the OAM property of the beam’s electromagnetic wave components. A beam pointing in a certain azimuth direction was optimized by superpositioning waves with different OAM orders; the beam direction was controlled by the relative phase shifts between the waves. By linking the OAM wave generators to a Maxwell fish-eye lens, the beam’s elevation could be independently regulated. Over a large spatial steering range, the suggested antenna worked with good directivity, small beamwidth, and low sidelobe levels. The steering method in [13] is based on superimposing several OAM waves. The waves are produced using waveguide resonators. The main concern in this design is the limited number of OAM waves that can be used [13]. The nature of the resonating structure implies that the resonators correspond to different OAM waves being stacked axially on top of each other, instead of being installed in the same plane, which leads to distortions in the resulting superimposed beam. In summary, the need for multiple loops to create an OAM superposition in [11], and the need for a lens to direct the radiation in [12], in addition to the limited number of OAM waves that can be used in [13] raise the question of the possibility of having a simpler method that utilizes the full capabilities of OAM waves for beam steering. In contrast to the methods mentioned above, we explore in this paper exploiting the divergence property of OAM waves as a property for independent control of the azimuthal and elevation beam directions. Firstly, OAM waves are generated in an array consisting of several concentric Planar Circular Dipole (PCD) elements that are closely placed together. With appropriate feeding of the PCD elements, an OAM wave is produced with the capacity to achieve different orders, which will be clarified in the upcoming section. Elevation directions are managed according to the OAM orders, where it is known that a wave carrying higher OAM order deflects more from the mean propagation axis than a wave holding a lower order. On the other hand, the azimuthal radiation is focused in a certain desired direction by turning off some of the PCD elements in the array. These two techniques are combined for independent electrical steering in the elevation and azimuth planes.

This paper is structured as follows: Section 2 includes the detailed design characteristics of the antenna. Section 3 describes the beam steering method through the mathematical formulation of the system. Section 4 demonstrates the simulated results for essential beam generation and beam steering, which were obtained by Computer Simulation Technology (CST) Microwave Studio and MATLAB. Finally, the study’s conclusions are summarized in Section 5.

2  Antenna Configuration and Design

The system used for beam steering is introduced in the following two subsections. We deal first with the basic design of a PCD antenna element. Specifications related to overall size, radiation characteristics, and operation bandwidth are discussed. Then, in the second subsection, these PCD antenna elements are combined to build an array responsible for generating the OAM wave.

2.1 PCD Antenna Element Design

Fig. 1 shows a 3-D front view of the PCD antenna element, including the main configuration parameters. A material dielectric substrate of thickness (h)  of 1 mm and dielectric constant (ϵr) of 2.2 is installed. The length (L)  and width (W)  of the dielectric planar antennas are 50 mm and 30 mm, respectively. The gap () between the two circular geometric patch shapes is set to 0.5 mm. Two circular-shaped copper patches are placed over the dielectric substrate. The patch has a thickness of 0.1 × 10−4 mm and a radius (a) of 20 mm. The overall physical dimensions of the proposed antenna are given in Table 1. Using these parameters, a prototype of the proposed PCD antenna element was simulated using CST Microwave Studio with a convolutional perfectly matched layer, which was applied in all directions to minimize reflections. A simple edge port is used as a feeder. The space distance surrounding the antenna geometry was determined by the definition of the far-field region in [21]. The antenna provided a good matching range of 100 Ω from 3 GHz to about 30 GHz. This can be realized in Fig. 2, where the impedance bandwidth (10 dB return loss) is shown. This wide bandwidth of 27 GHz makes the proposed antenna promising for applications in ultra-wide bands and the new standard of broadband wireless 5G frequency bands (mm-wave).

Figure 1: Geometries of the 3-D PCD antenna element

Figure 2: Simulated return loss for the proposed antenna shown in Fig. 1

Generally, a dipole antenna with a good radiation pattern has an adequate length of 0.48λ , where λ is the wavelength. In this design, the dipole antenna’s effective length was related to the primary axis 4 a of the two circulars. According to the starting operating frequency of 3 GHz, the maximum λ was 100 mm. Thus, the effective length of this antenna was 0.45λ, which was smaller than 0.48 λ .

The proposed antenna was found to have a frequency ratio of 1:10 for the impedance bandwidth obtained. This behavior can be primarily attributed to achieving a more uniform current distribution in the proposed antenna, as shown in Fig. 3.

Figure 3: Simulated surface current distributions for the proposed antenna shown in Fig. 1 at 3 GHz

The radiation characteristics of the proposed antenna are also analyzed. Fig. 4 plots the simulated radiation pattern at 3 GHz. The gain variations in the azimuthal plane (x-y plane) greatly depend on the operating frequency; Fig. 5 shows the simulated gain for frequencies across the obtained impedance bandwidth. The antenna gain monotonically increases from approximately 2 to 5.5 dBi.

Figure 4: Simulated radiation patterns (E and H planes) at 3 GHz for the proposed antenna shown in Fig. 1

Figure 5: Simulated gain for the proposed antenna shown in Fig. 1

2.2 Array Design

An electromagnetic wave carrying OAM exhibits a helical phase-front due to the azimuthal dependency of its spatial phase distribution. This distribution is described in the form eim∅ , where i  is the imaginary unit number, m  is the OAM order (m=0,±1,±2,…) , and ∅ is the azimuthal angle. These waves are radially symmetric with a singularity at the wave center along the propagation axis [11,12]. To generate the phase profile of the OAM wave, we arranged an array of the PCD antenna elements described in the previous section. A sufficient number of PCD elements (N) should be used in the array such that |mmax|≤N/2 , where mmax  is the maximum OAM order provided by the array. To enforce the phase profile of the OAM wave, the PCD elements are distributed over a circular circumference, and each PCD element is excited by a constant phase offset from its neighbors. The needed phase offset to generate a wave at an order m is 2πNm. The complete design of an array is shown in Fig. 6, including nine radiation PCD elements. This design is theoretically able to produce the following OAM orders: {0,±1,±2,±3,±4} . Table 2 lists the initial phases of the ports for nine radiation PCD elements shown in Fig. 6 under various Δφ .

Figure 6: Circular array configuration including nine radiation PCD elements with disk reflector

3  System Mathematical Model

To understand the propagation properties of the radiation produced by the proposed method, a mathematical formulation of the design and the generated wave are provided in this section. As stated in the previous section, the initial beam is constructed from a Bessel beam of OAM order m. The amplitude of the beam in the transverse propagation plane is characterized by a Bessel function of the first kind and mth order Jm(⋅) . Thus, in cylindrical coordinates (ρ,ϕ,z) , the beam takes the form Jm(βρ)eimϕ, with β being the radial wave number, which is characterized by the separation relation that relates the radial and longitudinal wave numbers with the medium properties. The beam in this form is understood as an ideal field, owing to some unphysical properties, such as its infinite total energy and an infinite range of propagation. A more “realistic” form of the field, called a pseudo-nondiffracting field, is the subject of our interest as it models fields that can be generated in an experiment. As a typical representation of such a model, the Bessel-Gauss amplitude is adopted. Herein, the Bessel beam is modulated by a Gaussian envelope of waist radius w0  in e−ρ2/wo .

Having the field model under consideration, we proceed to form a beam by focusing the radiation in one direction. This is attained by partially annihilating the total radiation through pinning N -nulls at locations specified by the turned-off PCD antenna elements. These nulls are distributed in the array (z = 0) plane at ρneiϕn  for n∈[1,N] . Accordingly, the initial field distribution can be written as a whole in the form:

vo(ρ,∅)=Jm(βρ)eim∅e−ρ2wo2∏n=1N⁡(ρei∅−ρnei∅n). (1)

Fig. 7 shows, as an example, the (normalized) field intensity of a second-order OAM wave. In the upper part of the figure, where all elements of the array were activated, the radiation appears in the OAM expected form as a complete annular ring. Whereas, the lower part of the figure shows five nulls, which represent those PCD elements that were turned off; clearly, part of the previously shown complete intensity ring is dismissed now.

Figure 7: Normalized wave intensity for an OAM wave (m = 2) produced by an array of nine elements

The products in expression (1) can be reformulated as a sum of terms:

∏n=1N⁡(ρei∅−ρnei∅n)=∑n=0N⁡(−1)n(rei∅)N−nBn, (2)

where B0=1 , and

Bn=∑j1=1N⁡∑j2=j1+1N⁡⋯∑jn=jn−1−1N⁡∏n¯=1n⁡ρjn¯ei∅jn¯, (3)

for n≥1 . This change of form into a sum of terms simplified the analytical expression for the field upon propagation, as the different terms in the sum can be transformed separately. The standard Fresnel formula [22] determines how the field vo(ρ,ϕ)  propagates in the medium. Considering paraxial approximation with the z -axis as the mean axis of propagation, the field distribution at distance z is

v(ρ,∅,z)=−i exp[ ik(z+ρ22z) ]λz∫0∞∫02πvo(ρ´, ∅´)×exp[ ik2zρ´2−ikzρρ´cos(∅´−∅) ]ρ´dρ´d∅´, (4)

where k=2π/λ . After substituting the initial field vo(ρ,∅) and letting ∅´−∅=φ−π/2 , the result is casted as

v(ρ,∅,z)=2π−iexp[ik(z+ρ22z)]λz∑n=0N⁡Bn(−1)n(−i)m+N−n×exp[i(m+N−n)∅]×∫0∞Jm(βρ´)J(m+N−n)(kzρρ´)exp[(ik2z−1wo2)ρ´⁡2]ρ´⁡dρ´, (5)

where an additional Bessel function appeared after using the integral form [23]:

Jm(x)=12π∫02π⁡exp[i(mφ−xsin⁡φ)]dφ (6)

The radial integration in v(ρ,ϕ,z)  is obtained with the aid of Eq. (6.633.1) in reference [23]:

∫0∞⁡Jm(βρ′)Jm+N−n(kzρρ′)exp[(ik2z−1wo2)ρ′2]ρ′dρ′=βmγm+N−nα−(m+N−n+1)22m+N−n+1Γ(m+N−n+1)×∑l=0∞⁡Γ(l+m+N−n+1)l!Γ(l+m+1)(−β24α)l×F(−l,−m−l;m+N−n+1;(α/β)2). (7)

This expression is valid for (m+N−n)>−1 . On the right-hand side appears Γ(⋅) , the gamma function, F(.) , the hypergeometric function, in addition to α=1/wo2−ik/2z , and γ=kρ/z .

4  Results and Analysis

To appreciate the capability of the steering method and to evaluate the credibility of the derived system model, we provide in this part results obtained from numerical simulations using CST Microwave Studio and MATLAB. Firstly, essential OAM wave generation is considered using an array of PCD. Then, we deal with beam steering as a method based on the generated OAM waves.

4.1 OAM Wave Generation

Following the design criteria, nine radiation PCD elements are placed over a circular circumference with a radius of 80 mm. Upon appropriate feeding of the PCD elements, an OAM wave is generated. The radiation pattern for a second-order OAM wave (m = 2) is shown in Fig. 8. The OAM properties of the generated wave are demonstrated through phase and amplitude distributions in Figs. 9a and 9b, respectively. The phase distribution in Fig. 9a shows two complete 2π  cycles, which is consistent with theoretical predictions of OAM waves. In Fig. 9b, the change in the amplitude color from blue to red indicates an increase in the field value. The deep blue at the center indicates a null.

Figure 8: The simulated radiation pattern of an OAM wave (m = 2) at 3 GHz

Figure 9: Phase and amplitude distributions of an OAM wave ( m = 2) at 3 GHz

4.2 Beam Steering Based on OAM Waves

Azimuthal and elevation beam steering are attained electrically by controlling the excitation of the array of PCD elements. When a group of the PCD elements is turned off, the radiation is confined to a small part of the intensity ring. This is demonstrated in Fig. 10. When three array PCD elements (1, 8, and 9) are turned off, the radiated intensity (which formed a complete ring, see Fig. 7) is forced to follow a specific path (30° azimuthal angle in Fig. 10). Changing the off PCD elements changed the radiation azimuthal direction. Two more examples are shown in Figs. 11 and 12 for 90° and 210° azimuthal steering, respectively.

Figure 10: 3-D simulated radiation pattern at 3 GHz. directivity beam steering at a 30° azimuthal angle was achieved by turning off three array PCD elements (1, 8, and 9)

Figure 11: 3-D simulated radiation pattern at 3 GHz. Directivity beam steering at a 90° azimuthal angle was achieved by turning off three array PCD elements (1, 2, and 3)

Figure 12: 3-D simulated radiation pattern at 3 GHz. Directivity beam steering at a 210°azimuthal angle was achieved by turning off three array PCD elements (4, 5, and 6)

The polar plot given in Fig. 13 demonstrates the ability of the designed configuration to steer the beam over different elevations. The steering method, as explained previously, relies on changing the excitation phase to change the wave OAM order. This, in turn, confines the radiation to different elevations. A wave carrying a higher OAM order diverged more than one with a smaller order. This intrinsic property of the OAM wave is exploited to focus the beam onto the desired elevation. Regarding the elevation step size, it is clear from Fig. 13 that this step is limited to a minimum resolution, which might not be sufficient for specific scanning applications. To obtain finer control of the step size, it is suggested (even not studied in this paper) that fractional OAM orders are used; this, however, needs further modification to the OAM wave generation method. Another solution could be raising the array aperture size or, equivalently, the number of PCD elements in the array. This would make it possible to focus the radiation over a smaller dynamic range with smaller elevation steps between successive OAM orders. Two scenarios are deployed to prove the previous concept, as demonstrated in Fig. 14. In the first scenario, eighteen PCD elements are set up in the array leading to a change in elevation angle from 12° to 18° in corresponding to OAM order change from m = 2 to 3, respectively. In the second scenario, nine PCD elements are installed, leading to a more significant jump in the elevation angle from 17° to 43°, using the exact order change as in the first scenario. The following two findings should also be noted: 1) when the OAM order approaches the maximum limit that is allowed by the number of elements in the array, the side lobes begin to rise notably. This is obvious in Fig. 13, by noting that the 6th. OAM order has a relatively larger side lobe than the other (lower) orders. 2) An enhancement in the gain by 3.5 dBi is achieved upon turning some array elements off. For instance, the gain changed from 8 dBi when no elements were turned off (see Fig. 8) to 11.4 dBi when three elements were turned off (see Figs. 10–12). This rise in gain can be explained as the turned-off elements functioning as reflectors that enhance the energy flow in the steered beam direction.

Figure 13: A polar plot of the normalized beam steering radiation characteristic of the eighteen PCD elements with different OAM orders

Figure 14: Polar plots of normalized beams for different PCD element numbers and OAM orders. The resolution of elevation scanning can be increased by raising the PCD elements in the array

Fig. 15 shows the field distribution over a cross-section taken perpendicular to the propagation axis at 3 m from the array. The CST Microwave Studio simulation result of the propagated field is shown in Fig. 15a. A similar result is shown in Fig. 15b, obtained using MATLAB to plot the field derived in the mathematical model of Section 3. The results are comparable to a reasonable extent. However, some differences can be attributed to the nulls used in modeling the turned-off antenna elements. In contrast, the nulls were just considered in the mathematical model as points in the field distribution, the actual size of an off element is larger than being just a point.

Figure 15: Transverse section showing the hotspot of a beam after propagation by 3 m. The beam was steered over the horizon and directed toward a specific elevation using an OAM wave (m = 2)

In the next step, we expand the comparison to include performance comparison based on the OAM steering technique. In this case, comparing structure size, bandwidth, beam scanning dimensional, and elevation scanning resolution have been considered. Table 3 summarizes the results. The systems in [11–13] are considered in the comparison.

5  Conclusions

In this paper, we presented a simple method for electrically steering electromagnetic radiation in specific elevations and azimuthal directions. Constructing an OAM beam and annihilating part of it offered a wide dynamic steering range. Essential antenna elements of the array were designed to increase the system frequency range of operation and enhance the efficiency of radiation. We evaluated electrical beam steering by generating an OAM wave using PCD array antennas at 3 GHz as a testing point from a wide bandwidth range between 3 and 30 GHz. By achieving different OAM orders, we obtained different elevation directions. We could focus the radiation on a specific azimuthal direction by pinning N-nulls in the field of the generated wave by turning off some PCD antenna elements. Such focusing caused an increase in gain from 8.5 dBi to approximately 11.5 dBi. The system was mathematically and numerically modeled and studied under propagation conditions. Several aspects, including the elevation scanning resolution, were studied.

Funding Statement: The authors received no specific funding for this study.

Conflicts of Interest: The authors declare that they have no conflicts of interest to report regarding the present study.

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